Switch driver for a snubber circuit, method of operation thereof and power converter employing the same

ABSTRACT

In a power converter having a power switch, a rectifier and a snubber circuit having an auxiliary switch that moderates reverse recovery currents associated with the rectifier, a driver for the auxiliary switch, a method of driving the auxiliary switch and a power converter employing the driver and method. In one embodiment, the driver includes a first driver switch, coupled between the power switch and the auxiliary switch, that allows the auxiliary switch to turn on concurrently with the power switch. The driver also includes a second driver switch, coupled between the auxiliary switch and an output of the power converter, that prevents a voltage of the auxiliary switch from rising above an output voltage of the power converter to assist the auxiliary switch in turning off.

CROSS-REFERENCE TO RELATED APPLICATION

This application is related to U.S. patent application Ser. No.09/141,783, entitled "A SNUBBER CIRCUIT FOR A RECTIFIER, METHOD OFOPERATION THEREOF AND POWER CONVERTER EMPLOYING THE SAME," commonlyassigned with the present application and filed Aug. 28, 1998.

TECHNICAL FIELD OF THE INVENTION

The present invention is directed, in general, to power supplies and,more specifically, to a switch driver for a snubber circuit, method ofoperation thereof and power converter employing the same.

BACKGROUND OF THE INVENTION

A power converter is a power processing circuit that converts an inputvoltage waveform into a specified output voltage waveform. Aswitched-mode power converter is a frequently employed power converterthat converts an input voltage waveform into a specified output voltagewaveform. A boost power converter is one example of a switched-modeconverter that converts the input voltage to an output voltage that isgreater than the input voltage. Typically, the boost power converter isemployed in off-line applications wherein power factor correction isrequired and a stable regulated voltage is desired at the output of thepower converter.

A non-isolated boost power converter generally includes an energystorage device (e.g., an inductor) coupled between the input voltage andswitching device. The switching device is then coupled to an outputrectifier (e.g., a power diode) and an output capacitor. The load isconnected in parallel to the capacitor. Again, the output voltage(measured at the load) of the boost power converter is always greaterthan the input voltage. When the switching device is conducting, thediode is reverse biased thereby isolating the output stage. During thisperiod, the input voltage supplies energy to the inductor. When theswitching device is not conducting, the output stage receives the energystored in the inductor for delivery to the load coupled to the output ofthe converter.

Analogous to all types of power converters, a boost converter is subjectto inefficiencies that impair the overall performance of the powerconverter. More specifically, the rectifying diode suffers from areverse recovery condition thereby producing excessive power losses inboth the rectifying diode and the switching device and oscillations inboth current and voltage therefrom. The effect of the reverse recoverycondition is more severe in non-isolated converters, such as the boostpower converter. The reverse recovery condition can also detrimentallyaffect the longevity of the components, especially the rectifying diodeand switching device, of the boost power converter. Therefore, effortsto minimize the losses associated with the rectifier and switchingdevice and, more specifically, with the rectifying diode will improvethe overall performance of the power converter.

A traditional manner to reduce the losses associated with the rectifyingdiodes is to introduce a snubber circuit coupled to the rectifyingdiodes. Snubber circuits are generally employed for various functionsincluding to minimize overcurrents and overvoltages across a deviceduring conduction and non-conduction periods and to shape the deviceswitching waveforms such that the voltage and current associated withthe device are not concurrently high. For instance, with respect torectifying diodes, a snubber circuit may be employed to minimizeoscillations in both voltage and current and power losses associatedtherewith due to reverse recovery currents resulting from a snap-off ofthe rectifying diode during a transition from a conduction tonon-conduction mode of operation.

Snubber circuits are well known in the art. One approach to reduce thereverse recovery currents of the rectifying diode is to employ a snubbercircuit that includes an inductor in series with the rectifying diode.This type of snubber circuit attempts to recover the energy stored inthe snubber inductor during the reverse recovery period of therectifying diode for delivery to the output of the converter. While theinductor snubber provides an alternative for reducing the reverserecovery currents of the rectifying diode, there are tradeoffs in theselection of the inductor and auxiliary components of the snubber thatdetract from the advantages of employing such a snubber circuit.

For medium and high power applications, it may be advantageous to employa pulse width modulated (PWM) boost converter operating in a continuousconduction mode (CCM). It has been identified, however, that theefficiency and maximum switching frequency of a conventional PWM boosttopology is limited by the losses resulting from the reverse recoverycurrents of the output rectifier. A simple way of minimizing theselosses is to limit the rate of change of the current (di/dt) through theoutput rectifier as it turns off. Different alternatives have beensuggested to implement this solution. For cost sensitive applications, apassive snubber (such as the inductor snubber described above) may beused. For applications where higher efficiency is necessary, an activesnubber circuit may be employed in the PWM boost converter.

Active snubber circuits generally employ a switch and driving circuitryand energy recovery components. While active snubbers enjoy efficiencyimprovements over passive snubbers, the efficiencies may still furtherbe improved. This is especially important in view of the more arduousoperating conditions for the power converters thereby amplifying thenecessity for higher efficiency converters. In many applications, forinstance, power supplies are subject to environments having a wide rangeof temperatures in a convection or conduction cooling environment (i.e.,no fans). Therefore, improved converter efficiencies are becomingmandatory to meet difficult conditions thereby further supporting theneed for more efficient snubber circuits that temper losses in theconverter such as reverse recovery currents from the output rectifier.

Active snubber circuits typically require more elaborate ways ofcontrolling the active snubber switches, which also adds to thecomplexity of their use over the more operationally simple passivesnubber circuits. This is reflected in the necessary driver circuitryused to control the active snubber switches. If one or more of theactive snubber switches used is not referenced directly to the "lowside" or "current-return side" of the converter, the level of drivercomplexity increases since that particular active snubber switch drivesignal must be referenced to match the requirements of the activesnubber switch that it is driving in order to function properly. Thisoperational complexity typically negates some of the advantages gainedthrough the use of active snubber switches and results in increasedproduct costs.

Accordingly, what is needed in the art is a circuit that moderates areverse recovery current of a rectifier that maintains the advantagesassociated with lossless snubber circuits, but overcomes thedeficiencies presently available in the design thereof, and a costeffective way of driving one or more of the switches therein.

SUMMARY OF THE INVENTION

To address the above-discussed deficiencies of the prior art, thepresent invention provides, for use with a power converter having apower switch, a rectifier and a snubber circuit having an auxiliaryswitch that moderates reverse recovery currents associated with therectifier, a driver for the auxiliary switch, a method of driving theauxiliary switch and a power converter employing the driver and method.

In one embodiment, the driver includes a first driver switch, coupledbetween the power switch and the auxiliary switch, that allows theauxiliary switch to turn on concurrently with the power switch. Thedriver also includes a second driver switch, coupled between theauxiliary switch and an output of the power converter, that prevents avoltage of the auxiliary switch from rising above an output voltage ofthe power converter to assist the auxiliary switch in turning off.

The present invention introduces a switch driver for an auxiliary switchof a snubber circuit. The first driver switch allows the auxiliaryswitch conduct concurrently with the power switch. The second driverswitch prevents the voltage of the auxiliary switch from rising abovethe output voltage of the converter thereby assisting the turn-off ofthe auxiliary switch. The switch driver therefore provides a lesscomplex yet reliable system to drive the auxiliary switch.

In one embodiment of the present invention, the auxiliary switch is afield-effect transistor (FET). The second driver switch prevents a gatevoltage of the auxiliary switch from rising above the output voltage ofthe power converter. The switch driver of the present invention isapplicable to any switching device including a FET.

In an embodiment to be illustrated and described, the first and seconddriver switches are diodes. Of course, any type of switching device iswell within the broad scope of the present invention.

In one embodiment of the present invention, the rectifier includes apower diode. While the rectifier to be illustrated and described is apower diode, it should be clear that other rectifying devices are wellwithin the broad scope of the present invention. For instance, activerectifying devices such as synchronous rectifiers may be employed toadvantage in the power converter of the present invention.

In one embodiment of the present invention, the power converter furtherincludes a filter coupled across the output. In an embodiment toillustrated and described, the filter is an output capacitor. The outputcapacitor filters a DC waveform at the output of the power converter.Those skilled in the art are familiar with such filters.

In one embodiment of the present invention, power converter is a boostconverter. Of course, the principles of the present invention areequally applicable to other power converter topologies that suffer fromreverse recovery losses associated with a rectifier employed therein.

The foregoing has outlined, rather broadly, preferred and alternativefeatures of the present invention so that those skilled in the art maybetter understand the detailed description of the invention thatfollows. Additional features of the invention will be describedhereinafter that form the subject of the claims of the invention. Thoseskilled in the art should appreciate that they can readily use thedisclosed conception and specific embodiment as a basis for designing ormodifying other structures for carrying out the same purposes of thepresent invention. Those skilled in the art should also realize thatsuch equivalent constructions do not depart from the spirit and scope ofthe invention in its broadest form.

BRIEF DESCRIPTION OF THE DRAWINGS

For a more complete understanding of the present invention, reference isnow made to the following descriptions taken in conjunction with theaccompanying drawings, in which:

FIG. 1 illustrates a schematic diagram of a conventional PWM boostconverter employing an active snubber circuit;

FIG. 2 illustrates a schematic diagram of an embodiment of a threeswitch (3S) reduced-voltage/zero-current(RV/ZC-transition (T) PWM boostconverter constructed according to the principles of the presentinvention;

FIG. 3 illustrates a diagram of current and voltage waveforms of theboost converter of FIG. 2; and

FIG. 4 illustrates a schematic diagram of another embodiment of a threeswitch (3S) reduced-voltage/zero-current(RV/ZC-transition (T) PWM boostconverter constructed according to the principles of the presentinvention.

DETAILED DESCRIPTION

Referring initially to FIG. 1, illustrated is a schematic diagram of aconventional PWM boost converter employing an active snubber circuit.The conventional PWM boost converter includes a power switch Q1, a boostinductor Lo, a boost diode Do, an output capacitor Co and the activesnubber circuit which includes an auxiliary switch Q2, a capacitor C1,an inductor L1 and a diode D1.

The power switch Q1 of the PWM boost converter is alternately switchedon and off by a PWM signal thereby driving the boost operation for theconverter. The boost inductor Lo and the boost diode Do work in concertwith this action of the power switch Q1 to provide a DC output voltageVout which is filtered by the output capacitor Co. The value of theoutput voltage Vout is maintained by a regulating circuit (not shown)which adjusts the PWM waveform to the power switch Q1 to regulate theoutput voltage Vout.

The PWM boost converter operates in a continuous conduction mode (CCM)which means that an input current Iin, flowing through the boostinductor Lo, is essentially constant and is alternately routed betweenthe boost diode Do and the power switch Q1. The energy level of theoutput inductor Lo increases when the power switch Q1 is conducting, andthis incremental energy is delivered to the output load through theboost diode Do when the power switch Q1 is not conducting.

The reverse recovery of the boost diode Do is alleviated by the activesnubber circuit, which is activated just prior to the power switch Q1conducting, thereby channeling an increasing portion of the outputcurrent through the inductor L1 that was flowing through the boost diodeDo. This action eventually routes all of the output current, previouslyflowing through the boost diode Do, through the inductor L1 and thealternate switch Q2. The boost diode Do thereby turns off "softly", withminimal reverse recovery effects, eliminating the switching losses thatwould otherwise occur. Furthermore, the voltage across the power switchQ1 reduces to a value of substantially zero before the turn-on of thepower switch Q1. However, the active snubber circuit employs thealternate switch Q2 in a "hard" switching mode, which means that itturns-off with a non-zero voltage or current condition, causing highswitching losses itself and therefore, reducing the overall efficiencyof the boost converter.

Turning now to FIG. 2, illustrated is a schematic diagram of anembodiment of a three switch (3S)reduced-voltage/zero-current(RV/ZC)-transition (T) PWM boost converterconstructed according to the principles of the present invention. The 3SRV/ZC-T PWM boost converter, having an input current Iin, includes apower switch Q1, a boost inductor Lo, a rectifier (e.g., a power diode)Do, an output capacitor Co and a snubber circuit which includes firstand second auxiliary switches Q2, Q3, a snubber inductor Lr, a snubbercapacitor Cr, and first, second and third diodes D1, D2, D3. Thisembodiment of the present invention provides a power converter having aninput coupled to the power switch Q1 and the rectifier Do for conductingcurrents from the input to an output of the power converter. The snubbercircuit, employed in the power converter, provides a method ofmoderating reverse recovery currents associated with the rectifier Do.

The snubber circuit includes the snubber inductor Lr and the snubbercapacitor Cr coupled to the rectifier Do. The snubber circuit furtherincludes the first auxiliary switch Q2 that conducts to divert a portionof the current away from the rectifier Do through the snubber inductorLr and snubber capacitor Cr before the power switch Q1 transitions to aconducting state. Thus, the first auxiliary switch Q2 diverts and,ultimately, diminishes forward currents passing through the rectifier Doto thereby reduce reverse recovery currents associated with the turn-offof the rectifier Do. Furthermore, it provides The necessary conditionsto turn-on the power switch Q1 under substantially zero voltageconditions.

The snubber circuit still further includes a second auxiliary switch Q3,interposed between the power switch Q1 and the first auxiliary switchQ2, that conducts to create a path to discharge the snubber capacitor Crto the output at or before the power switch Q1 transitions to anonconducting state. The snubber capacitor Cr also provides a means ofresetting the snubber inductor Lr thereby allowing the first auxiliaryswitch Q2 to turn-off under a substantially zero current condition.Thus, the second auxiliary switch Q3 provides a path to recover aportion of the energy previously stored in the snubber capacitor Cr tothe output of the converter. The first and second auxiliary switches Q2,Q3 transition to a conducting state under a reduced voltage or currentcondition to reduce switching losses associated therewith. Thisembodiment results in a soft-switching operation of all majorsemiconductor components while reducing the circulating energy.

The snubber circuit still further includes the first diode D1 interposedbetween the snubber inductor Lr and the snubber capacitor Cr. Thesnubber circuit also includes the third diode D3 interposed between thesnubber inductor Lr and the second auxiliary switch Q3. Addition of thethird diode D3, provides a path to reset the inductor Lr and minimizethe interaction of the major parasitic components. Additionally, thesecond diode D2 is positioned in the path to discharge the snubbercapacitor Cr to the output.

While the rectifier Do is a power diode, it should be clear that otherrectifying devices are well within the broad scope of the presentinvention. For instance, active rectifying devices such as synchronousrectifiers may be employed to advantage in the power converter of thepresent invention. The power converter further includes a filter coupledacross the output in the form of the output capacitor Co. The outputcapacitor Co filters a DC waveform at the output of the power converter.

The output capacitance of the power switch Q1, the snubber capacitor Crand the snubber inductor Lr form a resonant, tank (tuned) circuit thatprovides zero voltage switching (ZVS) to the power switch Q1. A mainenhancement of this embodiment is that the first and second auxiliaryswitches Q2, Q3 turn on and turn off under soft conditions. The firstauxiliary switch Q2 turns off under zero current (ZC) conditions and thesecond auxiliary switch Q3 turns on and turns off under zero voltage(ZV) conditions. Furthermore, the snubber capacitor Cr appears inparallel with the power switch Q1 during its turn-off avoiding therequirement to add any external capacitance across it to slow down itsturn-off.

The turn-on of the first auxiliary switch Q2 defines the end of the "offtime" of the power stage (the power switch Q1 off). Due to the presenceof the snubber capacitor Cr and the first diode D1, the first auxiliaryswitch Q2 stops conducting naturally and remains in the off state untilthe power switch Q1 turns-off. Therefore, the first auxiliary switch Q2can be turned off at any time during this interval as long as the firstauxiliary switch Q2 turn-off occurs prior to the power switch Q1turn-off. The second auxiliary switch Q3 preferably is turned on beforethe power switch Q1 turns off and should be turned off before the firstauxiliary switch Q2 turns on (as will be shown in FIG. 3).

Turning now to FIG. 3, illustrated is a diagram of current and voltagewaveforms of the 3S RV/ZC-T PWM boost converter of FIG. 2. The timingsequence starts during the "off-time" of the power stage, showing thepower switch Q1 conducting with a gate-to-source voltage VGS1 positiveand a drain-to-source voltage VDS1 essentially zero. The drain-to-sourcecurrent IDS1 of the power switch Q1, which is also the input current Iinthrough the boost inductor Lo, is shown to be positive and increasingwith time. Additionally, the first auxiliary switch Q2 is not conductingwith a gate-to-source voltage VGS2 that is zero and a drain-to-sourcevoltage VDS2 also shown to be zero. The second auxiliary switch Q3 isalso not conducting with a gate-to-source voltage VGS3 at zero and adrain-to-source voltage VDS3 shown to be zero. The voltage VCR acrossthe snubber capacitor Cr is at its maximum value, and the current ILRthrough the snubber inductor Lr is seen to be zero. The gate-to-sourcevoltage VDG3 moves from zero to a positive value thereby placing thesecond auxiliary switch Q3 in a conducting mode prior to a time T0 asshown. This action allows the second auxiliary switch Q3 to turn onunder both a ZV and ZC condition and couples the drains of the powerswitch Q1 and the first auxiliary switch Q2 together.

At the time T0, the gate-to-source voltage VGS1 moves to zero causingthe power switch Q1 to become nonconducting. This action defines thestart of the "on-time" of the power stage. The input current Iin is nowinitially diverted through the second auxiliary switch Q3 since it isconducting, and begins discharging the snubber capacitor Cr as the inputcurrent Iin flows through it and the second diode D2 to the boostconverter output. When the voltage across the snubber capacitor Crdischarges to zero, the input current Iin is commutated to the rectifierDo. At this point, all of the input current Iin is flowing through therectifier Do to the boost converter output. This action also causes boththe drain-to-source voltages VDS1, VDS2 to rise to the value of theoutput voltage Vo when the discharge of the snubber capacitor Cr iscomplete at a time T1, as shown. After the time T1, the second auxiliaryswitch Q3 becomes nonconducting as the gate-to-source voltage VGS3 movesto zero allowing the second auxiliary switch Q3 to turn off under a ZVand ZC condition.

At a time T2, The first auxiliary switch Q2 starts conducting as thegate-to-source voltage VGS2 becomes positive. This action defines theend of the on-time of the power stage, and causes the input current Iinto begin diverting into the snubber inductor Lr, the first diode D1, thesnubber capacitor Cr and the first auxiliary switch Q2. As the currentincreases through the snubber inductor Lr from an initial value of zero,it reaches a value of the input current Iin at a time T3, as shown. Atthis point, the current flowing through the rectifier Do becomes zeroand it stops conducting allowing for a soft turn off of the rectifier Dowithout reverse recovery effects. Additionally, at the time T2, thedrain-to-source voltage VDS3 moves from zero voltage to the outputvoltage Vo since the first auxiliary switch Q2 starts conducting, andthe voltage VCR begins to increase as the snubber capacitor Cr charges.

At the time T3, the current ILR through the snubber inductor Lr hasincreased to a value of the input voltage Iin, as stated earlier, andcontinues to increase. The additional current is contributed from theoutput capacitance of the power switch Q1 since it is now isolated fromboth the input and the output of the boost converter. This action causesthe drain-to-source voltage VDS1 to decrease to zero. As thedrain-to-source voltage VDS1 becomes zero, the power switch Q1 actuallybecomes conducting before the gate-to-source voltage VGS1 goes positiveallowing it to turn on in a ZV condition. At a time T4, thegate-to-source voltage VGS1 becomes positive and the power switch Q1begins to divert current through itself. The drain-to-source currentIDS1 goes initially negative and then ramps up as the snubber capacitorCr charges and the current ILR through the snubber inductor Lrdiminishes. At a time T5, the snubber capacitor Cr is fully charged andthe drain-to-source current IDS1 assumes the value of the input currentIin, completing the cycle.

Turning now to FIG. 4, illustrated is a schematic diagram of anotherembodiment of a three switch (3S) reduced-voltage/zero-current(RV/ZC-transition (T) PWM boost converter constructed according to theprinciples of the present invention. The 3S RV/ZC-T PWM boost converter,having an input current Iin, includes a power switch Q1, a boostinductor Lo, a rectifier (e.g., a power diode) Do, an output capacitorCo, a snubber circuit which includes first and second auxiliary switchesQ2, Q3, a snubber inductor Lr, a snubber capacitor Cr, and first, secondand third diodes D1, D2, D3 and a gate drive circuit including first andsecond driver switches D4, D5. This embodiment of the present invention,which is similar to FIG. 2, provides a power converter having an inputcoupled to the power switch Q1 and the rectifier Do for conductingcurrents from the input to an output of the power converter. The snubbercircuit, employed in the power converter, provides a method ofmoderating reverse recovery currents associated with the rectifier Do.

The snubber circuit includes the snubber inductor Lr and the snubbercapacitor Cr coupled to the rectifier Do. The snubber circuit furtherincludes the first auxiliary switch Q2 that conducts to divert a portionof the current away from the rectifier Do through the snubber inductorLr and snubber capacitor Cr before the power switch Q1 transitions to aconducting state. Thus, the first auxiliary switch Q2 diverts and,ultimately, diminishes forward currents passing through the rectifier Doto thereby reduce reverse recovery currents associated with the turn-offof the rectifier Do. Furthermore, it provides The necessary conditionsto turn-on the power switch Q1 under substantially zero voltageconditions.

The snubber circuit still further includes a second auxiliary switch Q3,interposed between the power switch Q1 and the first auxiliary switchQ2, that conducts to create a path to discharge the snubber capacitor Crto the output at or before the power switch Q1 transitions to anonconducting state. The snubber capacitor Cr also provides a means ofresetting the snubber inductor Lr thereby allowing the first auxiliaryswitch Q2 to turn-off under a substantially zero current condition.Thus, the second auxiliary switch Q3 provides a path, to recover aportion of the energy previously stored in the snubber capacitor Cr, tothe output of the converter. The first and second auxiliary switches Q2,Q3 transition to a conducting state under a reduced voltage or currentcondition to reduce switching losses associated therewith. Thisembodiment results in a soft-switching operation of all majorsemiconductor components while reducing the circulating energy.

The snubber circuit still further includes the first diode D1 interposedbetween the snubber inductor Lr and the snubber capacitor Cr. Thesnubber circuit also includes the third diode D3 interposed between thesnubber inductor Lr and the second auxiliary switch Q3. Addition of thethird diode D3, provides a path to reset the inductor Lr and minimizethe interaction of the major parasitic components. Additionally, thesecond diode D2 is positioned in the path to discharge the snubbercapacitor Cr to the output.

In this embodiment, the gate drive circuit, including the first andsecond driver switches D4, D5, is used to control the main power switchQ1 and the second auxiliary switch Q3. As seen in FIG. 4, the secondauxiliary switch Q3 is not referenced to the low side of the converteras are the main power switch Q1 and the first auxiliary switch Q2. Thiscondition usually necessitates that a "high side driver" be used tocontrol the second auxiliary switch Q3, which would typically use eithera transformer or a transistor device requiring a somewhat complexcontrol circuit. The current embodiment of the present invention allowsboth the main power switch Q1 and the second auxiliary switch Q3 to becontrolled using diodes as driver switches, which are both simple andcost effective.

The first driver switch D4 allows the second auxiliary switch Q3 to beturned-on at the same time as the main power switch Q1, which meets theconditions of soft switching previously discussed. The second auxiliaryswitch Q3 only needs to be conducting during the turn-off of the powerswitch Q1, which allows the energy stored in the snubber capacitor Cr tobe delivered to the converter output as it discharges through the secondauxiliary switch Q3 and the second diode D2. The second driver switch D5turns the second auxiliary switch Q3 off when the snubber capacitor Crhas delivered all of its stored charge to the output through the seconddiode D2. The voltage across the snubber capacitor Cr is comparable tothe voltage across a gate capacitance Cg of the second auxiliary switchQ3 since they are essentially in parallel at this point.

As the snubber capacitor Cr continues to discharge, the gate capacitanceCg of the second auxiliary switch Q3 also continues to discharge. Thesecond drive switch D5 clamps the gate of the second auxiliary switch Q3to the converter output voltage. The drain voltages of the main powerswitch Q1 and the first auxiliary switch Q2 both rise to the value ofthe output voltage as they turn-off, which completely discharges thegate capacitance Cg of the second auxiliary switch Q3 causing it toturn-off. The first driver switch D4 provides isolation for the gate ofthe second auxiliary switch Q3 from the gate of the main power switch Q1at this time. In summary, the first driver switch D4 is in the turn-onpath and the second driver switch D5 is in the turn-off path for thesecond auxiliary switch Q3.

Of course, those skilled in the art should understand that thepreviously described embodiments of the snubber circuit (and convertertopologies and power supplies employed therewith) and switch drivers aresubmitted for illustrative purposes only, and other embodiments capableof reducing a reverse recovery current of a rectifier, other convertertopologies and other driver circuits are well within the broad scope ofthe present invention. For a better understanding of power electronics,power converter topologies, such as the boost power converter, andsnubber circuits see Principles of Power Electronics, by J. Kassakian,M. Schlecht, Addison-Wesley Publishing Company (1991), High EfficiencyTelecom Rectifier Using a Novel Soft-Switching Boost-Based Input CurrentShaper, by R. Streit, D. Tollik, IEEE Intelec Conference Records, pages720-726 (1991), Novel Zero-Voltage-Transition PWM Converters, by G. Hua,C. S. Leu, F. C. Lee, IEEE Power Electronics Specialists IntelecConference Records, pages 55-61 (1992), Soft Transitions Power FactorCorrection Circuit, by I. D. Jitaru, In the Proceedings of HFPC, pages202-208 (1993), U.S. Pat. No. 5,313,382, entitled Reduced Voltage/ZeroCurrent Transition Boost Power Converter, by R. Farrington, issued May17, 1994 and commonly assigned with the present invention. Theaforementioned references are herein incorporated by reference.

Although the present invention has been described in detail, thoseskilled in the art should understand that they can make various changes,substitutions and alterations herein without departing from the spiritand scope of the invention in its broadest form.

What is claimed is:
 1. In a power converter having a power switch, arectifier and a snubber circuit having an auxiliary switch thatmoderates reverse recovery currents associated with said rectifier, adriver for said auxiliary switch, comprising:a first driver switch,coupled between said power switch and said auxiliary switch, that allowssaid auxiliary switch to turn on concurrently with said power switch;and a second driver switch, coupled between said auxiliary switch and anoutput of said power converter, that prevents a voltage of saidauxiliary switch from rising above an output voltage of said powerconverter to assist said auxiliary switch in turning off.
 2. The circuitas recited in claim 1 wherein said auxiliary switch is a field-effecttransistor, said second driver switch preventing a gate voltage of saidauxiliary switch from rising above said output voltage of said powerconverter.
 3. The circuit as recited in claim 1 wherein said first andsecond driver switches are diodes.
 4. The circuit as recited in claim 1wherein said snubber circuit further comprises a snubber inductor and asnubber capacitor coupled to said rectifier and said auxiliary switch.5. The circuit as recited in claim 1 wherein said rectifier comprises apower diode.
 6. The circuit as recited in claim 1 further comprising afilter coupled across said output.
 7. The circuit as recited in claim 1wherein said power converter is a boost converter.
 8. In a powerconverter having a power switch, a rectifier and a snubber circuithaving an auxiliary switch that moderates reverse recovery currentsassociated with said rectifier, a method of driving said auxiliaryswitch, comprising:coupling a first driver switch between said powerswitch and said auxiliary switch, said first driver switch allowing saidauxiliary switch to turn on concurrently with said power switch;coupling a second driver switch between said auxiliary switch and anoutput of said power converter; and preventing a voltage of saidauxiliary switch from rising above an output voltage of said powerconverter with said second driver switch to assist said auxiliary switchin turning off.
 9. The method as recited in claim 8 wherein saidauxiliary switch is a field-effect transistor, said second driver switchpreventing a gate voltage of said auxiliary switch from rising abovesaid output voltage of said power converter.
 10. The method as recitedin claim 8 wherein said first and second driver switches are diodes. 11.The method as recited in claim 8 wherein said snubber circuit furthercomprises a snubber inductor and a snubber capacitor coupled to saidrectifier and said auxiliary switch.
 12. The method as recited in claim8 wherein said rectifier comprises a power diode.
 13. The method asrecited in claim 8 further comprising filtering said output voltage. 14.The method as recited in claim 8 wherein said power converter is a boostconverter.
 15. A power converter, comprising:an input coupled to aninput inductor; a power switch, coupled to said input inductor, thatimpresses currents through said power converter; a rectifier forconducting said currents from said input to an output of said powerconverter; a snubber circuit, including:a snubber inductor and a snubbercapacitor coupled to said rectifier; a first auxiliary switch thatconducts to divert a portion of said currents away from said rectifierthrough said snubber inductor and said snubber capacitor; and a secondauxiliary switch, interposed between said power switch and said firstauxiliary switch, that conducts to create a path to discharge saidsnubber capacitor to said output of said power converter; and a switchdriver, including:a first driver switch, coupled between said powerswitch and said second auxiliary switch, that allows said secondauxiliary switch to turn on concurrently with said power switch; and asecond driver switch, coupled between said second auxiliary switch andsaid output of said power converter, that prevents a voltage of saidsecond auxiliary switch from rising above an output voltage of saidpower converter to assist said second auxiliary switch in turning off.16. The power converter as recited in claim 15 wherein said first andsecond auxiliary switches are field-effect transistors, said seconddriver switch preventing a gate voltage of said second auxiliary switchfrom rising above said output voltage of said power converter.
 17. Thepower converter as recited in claim 15 wherein said first and seconddriver switches are diodes.
 18. The power converter as recited in claim15 wherein said rectifier comprises a power diode.
 19. The powerconverter as recited in claim 15 further comprising a filter coupledacross said output.
 20. The power converter as recited in claim 15wherein said power converter is a boost converter.